Television synchronizing apparatus

ABSTRACT

In a synchronized digital horizontal deflection system generating at 2xf H , a first word is produced that is indicative of the length of one-half the period H between f H  rate horizontal sync pulses. A first f H  rate signal that is synchronized to the horizontal sync pulses is generated. The first f H  rate signal is time shifted by one-half of the period H, in accordance with the first word to produce a second f H  rate second signal. The first and second signals are multiplexed for generating a horizontal deflection control signal at 2xf H  rate that controls the retrace interval timing in a deflection circuit output stage.

The invention relates to a circuit that generates a train of higher frequency pulses synchronized to input synchronization pulses, such as may be used in a television apparatus.

Recently there has been an interest in displaying an interlaced type video signal such as of the NTSC standard, in a non-interlaced scanning format for reducing the effects of artifacts. Such displaying format generally requires deflection current switching at a frequency which is a multiple of the horizontal frequency, f_(H), of the horizontal sync pulses. In television systems using double-horizontal rate scanning format, for example, it may be required to generate two cycles of horizontal deflection current from each horizontal sync pulse. In comparison, in standard television systems, the correspondence is one cycle from each sync pulse.

In some prior art circuits, the doubling of the horizontal rate frequency is accomplished by a phase-lock-loop circuit that includes a voltage controlled oscillator (VCO). The output frequency of the VCO is equal to a multiple of the horizontal rate. In digital television, for example, it is desirable to generate the deflection current using signals that are derived from a common system clock, rather than from a VCO.

In accordance with an aspect of the invention, a periodic input signal that is indicative of a first periodic event such as, illustratively, the horizontal sync pulses, is used for generating a first signal that is indicative of the length of a part period of the synchronizing input signal, such as illustratively, 1/2 of the period H of the horizontal sync pulses. A second signal that is indicative of a second periodic event, such as occurring, illustratively, every period H at the rate of f_(H), is generated from the periodic input signal. A third signal that is indicative of a third periodic event, such as occurring, illustratively, every period H, is produced from the second signal by time shifting the second signal by an amount that is determined in accordance with the length of the part period. The third signal is used for generating a first component signal of an output signal. A second component signal of the output signal is generated from the input signal. The frequency of the output signal is greater than that of the input signal. The interval between corresponding events of a given pair of events of the second and third periodic events, respectively, is determined in accordance with the first signal. Such interval is, illustratively, equal to 1/2 of the period H. The output signal, such as used for controlling a deflection circuit output stage switch, is generated from the second and third signals at periodic instants that correspond with the second and third periodic events, respectively, of the second and third signals, respectively.

In carrying out a specific embodiment of the invention, for example, a driver circuit of a television deflection circuit that utilizes double horizontal rate scanning format, generates the output signal that forms deflection cycles in an output stage. A deflection cycle forming signal that is the second component signal of the output signal, generated from the second signal, appears at the horizontal rate, f_(H). Similarly, a deflection cycle forming signal that is the first component signal of the output signal, produced from the third signal, also appears at the horizontal rate, f_(H). However, the interval between adjacent deflection cycles formed by the two last mentioned deflection-cycle-forming first and second component signals, respectively, of the output signal, has the length of one-half of the period of the periodic input signal, in accordance with the length information contained in the first signal. Thus, the circuit doubles the frequency of the sync pulses to obtain, in the output stage, deflection current at the frequency of 24×f_(H).

The deflection circuit driver circuit includes, in accordance with another aspect of the invention, a phase-lock-loop circuit that is synchronized to the periodic input signal that contains the sync pulses. Each of the second and third periodic events is defined by the second and third signals, respectively, with a resolution of a fraction of a common clock signal period. Each period of the periodic input signal results in a corresponding sequence of states in the phase-lock-loop circuit. Each state is produced synchronously with the common clock signal.

The phase-lock-loop circuit supplies the second and third signals that are indicative of the second and third periodic events, respectively, to a phase-control-loop circuit for generating the deflection cycle forming output signal therefrom. The phase-control-loop circuit receives a retrace signal from the deflection circuit output stage for correcting, illustratively, only once during a given period of the periodic input signal, and in accordance with the timings of one signal of the second and third signals, the timings of the output signal. The output signal timings are corrected, so as to make the timings of the deflection cycles correspond with the second and third periodic events.

The tracking response time, in the phase-control-loop circuit, with respect to phase variations of the retrace signal is faster than the corresponding tracking response, in the phase-lock-loop circuit, with respect to phase variations of the periodic input signal that contains the sync pulses. This is so, because the phase-control-loop circuit is optimized to accommodate fast switching time variations in the output stage that may occur because of fast changing electron beam current; whereas the phase-lock-loop circuit is optimized to reject noise or jitter accompanying the sync pulses.

FIG. 1 illustrates a general block diagram of a deflection circuit that includes a phase-lock-loop circuit and a phase-control-loop circuit, embodying an aspect of the invention;

FIG. 2 illustrates a detailed block diagram of the deflection circuit of FIG. 1;

FIGS. 3a-3g illustrate timing diagrams useful in explaining the synchronization of the phase-lock-loop circuit of FIG. 2;

FIGS. 4a-4r illustrate timing diagrams that are useful for explaining the operation of the circuit of FIG. 2; and

FIG. 5 illustrates an embodiment of a phase comparator of FIG. 2.

FIG. 1 illustrates a block diagram of a horizontal deflection circuit including a phase-lock-loop circuit 20. It includes a sequential counter 21 that has the analogous function of a VCO of a conventional phase-lock-loop circuit. Counter 21 is a programmable counter that is incremented after each leading edge of a clock CK having a period t_(CK), illustrated in the timing diagram of FIG. 4a. It counts up, from an initial value of, for example, 1, until it is reset to the initial value by a reset pulse RESET at an input terminal 21a of FIG. 1. Pulse RESET controls the number of clock CK periods t_(CK) that are included in a corresponding period, or sequence, N, of counter 21. Successions of sequences N produced by counter 21 define a recurring sequence. Each word CT, at an output port 21b of counter 21, supplies, in a given sequence N, the current count of counter 21.

Illustratively, a digital word herein is represented as a base 2 number that includes an integer, a fraction or a combination of an integer and a fraction. A negative number is represented as a 2's complement number.

Horizontal sync pulses H_(s) having a period H (1H sync pulses H_(s)), are coupled, illustratively, from a conventional sync separator 60 of a television receiver to a phase detector 202. When phase-lock-loop circuit 20 is phase-locked to sync pulses H_(s), provided that they are accompanied by low level of noise, the leading edge of each pulse MS that is coupled to phase detector 202 occurs substantially coincidentally with the last clock CK edge that occurs before the center of the corresponding sync pulse H_(s). Pulse MS is generated by a decoder 23 when a predetermined value of word CT is detected. Thus, the center of each sync pulse H_(s) occurs a variable fraction f of clock CK period t_(CK) of FIG. 4a after the leading edge of pulse MS of FIG. 1.

Variable fraction f is contained in a 1H skew word SK that is also coupled to phase detector 202. Phase detector 202 generates a period length adjusting word LPFO. Word LPFO is combined, in a horizontal period length generator 33, with a constant word PR to produce a word DPW. Word PR, for example, equals the value 910 where 910×t_(CK) is equal to the nominal, or free-running period, of phase-lock-loop circuit 20. Note that clock CK period t_(CK) is equal to (1/4×f_(sc)) where f_(sc) is the NTSC color subcarrier frequency.

Word DPW contains the calculated estimate, or computed, binary value of the actual period H of pulses H_(s) in the form of an integer number M of clock CK period t_(CK) and a fractional number k of clock CK period t_(CK). Word DPW is coupled to a counter period and skew words generator 201 that generates 1H skew word SK and a period word PERIOD. Word PERIOD, that contains the number of clock CK cycles in a given counter 21 period N, is coupled to a comparator 200 that compares the current value of words CT and PERIOD and generates pulse RESET when word CT=word PERIOD. Pulse RESET initializes counter 21 to contain word CT=1 simultaneously with the next clock CK edge that, thereby, defines the end time of the current sequence N of counter 21 and the beginning time of the next sequence N.

Words CT are coupled through a programmable time shifter or delay 42 to provide delayed words Ca. The delay of programmable delay 42 is controlled by an external word NPW that is coupled from a source not shown in the Figures. A word CMa, defined to include words SK and Ca that provide the fraction and integer parts, respectively, of word CMa, is coupled to a programmable delay 203. A word CMao is defined as the state of word CMa in which word Ca=0. Word CMao defines a periodic event e_(CMao) having a period that is equal to an estimated value of the actual period H, in accordance with word DPW. Event e_(CMao) occurs f×t_(CK) after the leading edge of clock CK that causes word Ca to become zero, as described later on. Fraction f is the value contained in 1H skew word SK.

In accordance with an aspect of the invention, horizontal period length word DPW is coupled to a divide-by-2 unit 46 that divides the value of word DPW by the factor 2 to produce word HDPW that is indicative of one-half the horizontal period length H. Word HDPW is coupled to the control port of programmable delay 203 that delays event e_(CMao), defined by word CMao, by H/2 in accordance with the value of delay 203 control word HDPW.

A word CMb, the output word of programmable delay 203 includes a skew word SKB and a word Cb, providing the fraction and integer parts, respectively, of word CMb. A word CMbo is defined as the state of word CMb in which word Cb=0. Word CMbo defines a periodic event e_(CMbo) that occurs in the calculated estimate center of the interval between each pair of successive events e_(CMao).

Words CMa and CMb are coupled to ports 40a and 40b, respectively of a multiplexer 40. Multiplexer 40 couples, alternately, words CMa and CMb to input port 51a of a programmable time shifter or delay 51 of a phase-control-loop circuit 120. Words CMI and CMP, at an output port 51c of programmable delay 51, represent an integer and a fraction, respectively, of clock CK period t_(CK) of FIG. 4a. Words CMI are coupled to a horizontal drive pulse generator 253 that generates, each time word CMI=0, a pulse PGP having a width w that is controlled by an external word WIDTH. Pulse PGP is coupled from pulse generator 253 to an input terminal 54a of a gate delay 54. Gate delay 54 delays pulse PGP by a fraction q of clock CK period t_(CK) of FIG. 4a, having a length that is determined in accordance with the value of word CMP of FIG. 1, to produce a 2f_(H) rate signal HORDRIVE at an output terminal 54b of gate delay 54. Signal HORDRIVE is also coupled to a flip-flop unit 55. Each pulse of signal HORDRIVE causes the toggling of a signal TOGGLE at an output terminal 55a of flip-flop unit 55. Signal TOGGLE is coupled to a select terminal 40c of multiplexer 40. Signal TOGGLE causes, in accordance with its logical state, the alternate coupling of words CMa and CMb, respectively, to input port 51a of programmable delay 51. Thus, the timings of the pulses of signal HORDRIVE are controlled, alternately, by the words in ports 40a and 40b, respectively, of multiplexer 40.

It should be understood that an arrangement similar to the arrangement of FIG. 1 may be used for generating a signal analogous to signal HORDRIVE of FIG. 1 having a different multiple of the frequency f_(H) such as, illustratively, 3f_(H) or 4f_(H).

Signal HORDRIVE is coupled to an input terminal 41a of a 2f_(H) horizontal deflection circuit output stage 41 to control the switching of a horizontal output transistor. A retrace interval is formed in response to a corresponding pulse of signal HORDRIVE. A resulting pulse FLYBACK, occurring during retrace, that is obtained, illustratively, from a flyback transformer, not shown in FIG. 1, of output stage 41, is coupled to a phase detector 202'.

When phase-control-loop circuit 120 is perfectly phase-locked to flyback pulses FLYBACK, the leading edge of each pulse MS', that is also coupled to phase detector 202', occurs substantially coincidentally with the last clock CK edge before the center time of the respective pulse FLYBACK. Pulse MS' is generated by a decoder 23' when a predetermined value of word Ca is detected. The center of pulse FLYBACK occurs fraction f of clock CK period t_(CK) of FIG. 4a after the leading edge of pulse MS' of FIG. 1. Fraction f is contained in 1H skew word SK.

Phase detector 202' generates a word LPFO' that controls the delay time of programmable delay 51. Programmable delay 51 is capable of providing a positive or negative phase shift, or time delay, as explained later on. The center of 2f_(H) rate pulses FLYBACK occurs coincidentally with each corresponding event e_(CMao) or e_(CMbo). Even e_(CMao) occurs during the time in which word Ca=0; whereas event e_(CMbo) occurs when word Cb=0, as described before. Therefore, in accordance with a feature of the invention, the arrangement of FIG. 1 generates the 2f_(H) rate pulses FLYBACK, delayed by corresponding constant delay times relative to the corresponding 1H sync pulse H_(s).

FIG. 2 illustrates a more detailed block diagram of the arrangement of FIG. 1. Similar numerals and symbols in FIGS. 1 and 2 illustrate similar items or functions. FIGS. 4a-4r illustrate timing diagrams of a typical steady state example, showing three consecutive periods, or sequences, N_(a), N_(b) and N_(c) of counter 21 of FIG. 2, when phase-lock-loop circuit 20 is phase-locked to sync pulses H_(s) of FIG. 4r. Similar numbers and symbols in FIGS. 1, 2 and 4a-4r represent similar items or functions.

Assume that word DPW, at an input port 34a of an adder 34 of FIG. 2, contains the calculated estimate value of period H of horizontal sync pulses H_(s) of FIG. 4r. Word DPW of FIG. 2 includes, illustratively, 10-bit number, M, representative of an integer multiple of clock CK periods t_(CK) of FIG. 4a, and 5-bit number, k, representative of a fraction of period t_(CK). The value (M+k)×t_(CK) defines the updated estimate of period H.

Skew word SK, representing fraction f, at an output port 38b of a latch 38 of FIG. 2, is coupled, right justified, to an input port 34b of adder 34, where it is summed up with right justified word DPW. A word CNTPR appears at an output port 34c of adder 34 to represent the integer part of the addition result. Each bit of word CNTPR is at the same numerical weight as the corresponding bit of the integer part, M, of word DPW. Word CNTPR is coupled to an input port 35a of a latch 35. Latch 35 stores the value of word CNTPR, at a time T_(t) of FIG. 4f under the control of a pulse CL of decoder 23 of FIG. 2, to form period length word PERIOD at an input port 36a of a subtractor 36. Subtractor 36 controls the total number of states in a given counter 21 period N. Decoder 23 decodes counter 21 words CT and generates timing control signals such as pulse CL, as well as other timing pulses that are mentioned later on, when a corresponding predetermined state of counter 21 occurs. Pulse CL is also coupled to a clock input terminal 38a of latch 38 for storing, at time T_(t) of FIG. 4e, a word SKIN of FIG. 2 to produce 1H skew word SK that contains fraction f. The bits of fraction f appear at the same numerical scale, or weight, as the corresponding bits of fraction k of word DPW. Fraction f is representative of the fractional part of the addition result. Thus, adder 34 adds right justified latch 38 output word SK, that was formed by pulse CL during the immediately preceding period N of counter 21, to right justified word DPW, for updating words PERIOD and SK, respectively, at time T_(t) of FIGS. 4f and 4e, respectively.

Counter 21 output word CT of FIG. 2 is coupled to an input port 36b of subtractor 36 where it is subtracted from word PERIOD to form, in a port 36c, a word RS. Word RS is coupled to a zero detector 37. Zero detector 37 issues pulse RESET, as illustrated in FIG. 4j, when word RS of FIG. 2 is equal to zero. Thus, when counter 21 word CT is equal to counter 21 period word PERIOD, counter 21 is reset and the next counter 21 word CT is equal to 1, the initial counting state, Word PERIOD expresses, in multiples of clock CK periods t_(CK) of FIG. 4a, the length of period N of counter 21 of FIG. 2.

Word Ca, illustratively 10-bit wide, is obtained by subtracting, in a subtractor that represents programmable delay 42 of FIG. 1, the current word CT of counter 21 of FIG. 2 from constant word NPW. FIG. 4c illustrates an example of the corresponding sequence that is represented by words Ca. When word CT is equal to word NPW, word Ca is equal to 0. Similarly, when word CT exceeds word NPW by 1, word Ca is equal to 1023, in accordance with conventional 2's complement arithmetic. In each counter 21 sequence N, the states Ca=1, Ca=0 and Ca=1023 occur, respectively, as counter 21 of FIG. 2 is incremented sequentially. The time in which word Ca of FIG. 4c becomes zero is defined as time t_(CTJ). Time t_(CTJ) occurs (J-1) clock CK periods t_(CK) after sequence N beginning time, such as time T₀ of period N_(a). During clock Ck period t_(CK) that follows time T₀, counter 21 word CT is equal to 1. Word CMao is defined as the state of word CMa in which word Ca=0, as described before. Each word CMao thus defines periodic event e_(CMao) that occurs at time t_(CMao) =t_(CTJ) +fxt_(CK), as illustrated by the corresponding short arrows in FIG. 4d. Note that word SK of a given word CMao may have different values in corresponding counter 21 periods N. For example, during the interval t_(CK) that immediately follows time t_(CTJ) of FIG. 4e, word SK is equal to f₁. Thus, event e_(CMao) of FIG. 4d occurs at time t_(CMao) =t_(CTJ) +f₁ ×t_(CK). Note that fraction f₁ was computed during period N of counter 21 of FIG. 2, not shown in FIG. 4a-4r, that occurred immediately prior to period N_(a).

The arrangement of FIG. 2 computes the timing of the next event e_(CMao) of FIG. 4d, such as time t_(CMao) ' of event e_(CMao) ' relative to time t_(CTJ), by adding, in adder 34, old fraction f₁ of word SK of FIG. 2, to fraction k of word DPW to produce new fraction f₂. A binary carry C may be produced from such addition and The corresponding new period word PERIOD becomes (M+the value of carry C), at time T_(t) of FIG. 4f. The interval between successive events e_(CMao) of FIG. 4d is equal to (M+K)×t_(CK), as shown by the examples below.

Assume, hypothetically, that prior to time T_(t) of FIG. 4e the fractional result, word SKIN of FIG. 2=(f₁ +k), is <1; since no carry C is produced, word CNTPR is equal to M, the integer part of word DPW. After pulse CL of FIG. 2, occurs, at time T_(t) of FIG. 4e, word SK is equal to f₂ =(f₁ +k) and word PERIOD of FIG. 4f is equal to M. Since reset pulse RESET of FIG. 4j occurs when word CT of FIG. 2 is equal to word PERIOD, the length of counter 21 period N_(a) is going to be equal to (M) clock CK periods t_(CK) of FIG. 4a. The corresponding event e_(CMao) that occurs at time t_(CMao) of FIG. 4d during counter 21 period N_(a), occurs (J-1+f₁)×t_(CK) after beginning time T₀ of period N_(a) of FIG. 4b.

Assume, in a second hypothetical example, that prior to time T_(t) ' of FIG. 4e, the fractional result, word SKIN of FIG. 2=f₂ +k, is >1; consequently, carry C is produced in adder 34, and word CNTPR of is equal to (M+1). It follows that after pulse CL occurs, at time T_(t) ' of FIG. 4e, fraction f₃, represented by word SK of FIG. 4e, is equal to (f₁ +k)+k-1, and word PERIOD of FIG. 4f is equal to (M+1). Therefore, the length of counter 21 period N_(b) of FIG. 4b is going to be equal to (M+1) clock CK periods t_(CK). The corresponding event e_(CMao) ', during counter 21 period N_(b), occurs (J-1+f₁ +k)×t_(CK) after beginning time T₀ ' of period N_(b) of FIG. 4b.

Assume, in a third hypothetical example, that prior to time T_(t) ', the fractional result, word SKIN of FIG. 2=(f₁ +2k-1)+k, is <1; since no carry C is produced, word CNTPR is equal to M. It follows that after pulse CL occurs, at time T_(t) " of FIG. 4e, the corresponding word PERIOD of FIG. 4f is equal to M. Therefore, the length of counter 21 period N_(c) of FIG. 4b is going to be equal to (M) clock CK periods t_(CK). The corresponding event e_(CMao) " occurs (J-1+f₁ +2k-1)×t_(CK) after beginning time T₀ " of period N_(c) of FIG. 4b.

The above calculations lead to the conclusion that the interval t'_(CMao) -t_(CMao) of FIG. 4d, of successive events e_(CMao), is equal to:

    [T.sub.0 '-t.sub.CMao ]+[t.sub.CMao '-T.sub.0 ']=[M-(J-1+f.sub.1)]+[J-1+f.sub.1 +k]=(M+k)

of clock CK periods t_(ck). Likewise, the interval t"_(CMao) -t'_(CMao) is equal to:

    T.sub.0 "-t.sub.CMao ']+[t.sub.CMao "-T.sub.0 "]=[(M+1)-(J-1+f.sub.1 +k)]+[J-1+f.sub.1 +2k-1]=(M+k)

of clock CK periods t_(ck). Thus, the length of the interval between successive events e_(CMao) of FIG. 4d, is expressed in the content, (M+k), of word DPW of FIG. 2. The length of a given period N of FIG. 4b may be, for example, either (M) or (M+1) clock CK periods t_(CK) ; however, the average length of period N, is equal to period H of horizontal sync pulses H_(s) of FIG. 4r, as explained later on.

At time t_(CH) of FIG. 4g, which occurs prior to time T_(t) of period N_(a), fraction f in latch 38 of FIG. 2 is saved in a latch 45 to form a word SKD. The saving of word SK is done by a pulse CH from decoder 23. Word SKD is coupled, right adjusted, to an input port 47b of an adder 47 that is similar to adder 34. Word DPW, that contains (M+k), is coupled through divide-by-2 unit 46 that includes, for example, a right shifter, to the other input port of adder 47 to form there right adjusted word HDPW that is equal to (1/2)×(M+k). A word IHP, the integer part of the result of the addition in adder 47, is coupled to an input port 49a of an adder 49. Word Ca of programmable delay 42 is coupled to an input port 49b of adder 49 where it is added with word IHP to form word Cb. Skew word SKB of FIGS. 4g and 2 contains a fractional part g of the result of the addition of the respective fractions in adder 47.

Word Cb is equal to 0 during the length of clock CK period t_(CK) that immediately follows clock CK edge of a time t_(CTB) of FIG. 4h. Word CMbo of FIG. 2 that is defined as the state of word CMb in which word Cb=0, is thus defined in an analogous manner to the way word CMao was defined before. Similarly to words CMao, words CMbo define corresponding periodic events e_(CMbo) of FIG. 4i, that are analogous to events e_(CMao) of FIG. 4d. In an analogous manner, event e_(CMbo) of FIG. 4i, for example, occurs g×t_(CK) after time t_(CTB) of FIG. 4h.

As explained before, programmable delay 203 of FIG. 1, that is controlled by word HDPW, delays the occurrence of event e_(CMao) of FIG. 4d by a duration that is determined in accordance with the value of word HDPW of FIG. 2 to define event e_(CMbo) of FIG. 4i. Event e_(CMbo) is delayed by H/2 relative to the corresponding event e_(CMao) of FIG. 4d. In accordance with an aspect of the invention, each event e_(CMbo) of FIG. 4i occurs at the center of the corresponding interval that lies between consecutive events e_(CMao) of FIG. 4d, as shown by the example below.

During counter 21 period N_(a) of FIG. 4g, prior to time t_(CH), latch 45 of FIG. 2 contains fraction f₁. Since word HDPW is equal to (1/2)×(M+k), the addition result at port 47c of adder 47 is equal to (1/2)×(M+k)+f₁. Assume, hypothetically, that M is an odd number that is equal to 2A+1. The number A, an integer, is thus equal to (M-1)/2. It follows that (1/2)×(M+k)+f₁ is equal to (A+1/2+k/2+f₁). Further assume, hypothetically, that fraction g₁ of word SKB of FIG. 4g, that is equal to (1/2+k/2+f₁), is less than 1. Thus word IHP is equal to A, the integer part of word HDPW. Because of the summation of words IHP and Ca in adder 49, word Cb of FIG. 4h will be equal to zero when (A) clock CK periods t_(CK) have elapsed after time t_(CTJ) of FIG. 4c. Thus, event e_(CMbo) of FIG. 4i of time t_(CMbo) occurs (A)×t_(CK) +(1/2+k/2+f₁)×t_(CK) after time t_(CTJ) of FIG. 4c. The total delay time, T_(H/2a) in FIG. 4i, from time t_(CTJ) to the corresponding time t_(CMbo) is equal to [(M-1)/2+(1/2+k/2+f₁)]×t_(CK) =((M+k)/2+f₁)×t_(CK). Since event e_(CMao) occurs at time t_(CMao) =t_(CTJ) +f₁ ×t_(CK), it follows that event e_(CMbo) of FIG. 4i occurs (M=k)/2×t_(CK) after the immediately preceding event e_(CMao) of FIG. 4d. It can be shown that the same result is obtained when other assumptions are made with respect to M or fraction g₁. Since the period defined by successive events e_(CMao) is equal to (M+k), it follows that each event e_(CMbo) of FIG. 4i lies at the center of the interval t_(CMao) -t_(CMao) ' between consecutive events e_(CMao) and e_(CMao) ', respectively, of FIG. 4d. As described later on, and in accordance with an aspect of the invention, alternate retrace intervals, that are repeated every period H, occur in accordance with times t_(CMbo) of events e_(CMbo) of FIG. 4i. The other alternate retrace intervals occur in accordance with times t_(CMao) of events e_(CMao) of FIG. 4d.

Each f_(H) rate sync pulse H_(s) of FIG. 2 is sampled by clock CK and the corresponding sample is digitized in a digitizer unit 61, such as an analog-to-digital converter, to form, in a conventional manner, a corresponding word 207. Successive digitized sync words 207 are coupled to an input port 25a of a digital low pass filter 25. Successive digitized sync words SY, at the output of filter 25 are coupled to an input port 22a of a sync phase comparator 22. As described below, sync words SY are used for synchronizing each event e_(CMao) of FIG. 4d with the corresponding sync pulse H_(s) of FIG. 4r, and for obtaining period length word DPW of FIG. 2.

FIGS. 3a-3g illustrate schematically timing diagrams useful in explaining the synchronization of phase-lock-loop circuit 20 of FIG. 2. Similar symbols and numerals in FIGS. 2, 3a-3g, and 4a-4r illustrate similar items or functions. FIG. 3a illustrates an example of successive digitized sync words SY of FIG. 2 that result from digitizing an idealized trapezoidal horizontal sync pulse H_(s), defining a trapezoidal envelope 1, during interval T of FIGS. 4r and 3a. Envelope 1 of FIG. 3a has a leading edge 72 and a trailing edge 73, illustrated by dashed lines. During entire interval T, between times T_(b) and T_(e), respectively, each sync word SY appears after each leading edge of clock CK of FIG. 3d. Words SY are illustrated schematically by the vertical arrows that reach up to envelope 1, representing the respective magnitude of words SY.

Decoder 23 of FIG. 2 produces control pulse MS at time T_(m) of FIG. 3c or 4l when a predetermined value of word CT of FIG. 2 occurs, such as, for example when word CT is equal to 315. Control pulse MS is coupled to a terminal 22b of phase comparator 22 where it is phase-compared with a corresponding sync pulse H_(s) that forms words SY, as described below.

FIG. 5 illustrates schematically a block diagram of phase comparator 22. Similar symbols and numerals in FIGS. 1, 2, 3a-3g, 4a-4r and 5 indicate similar items or functions. Phase comparator 22 of FIG. 5 includes an accumulator 26 that substractively accumulates, from an initial value of zero, successive sync words SY of FIG. 3a from time T_(b), at the beginning of interval T of FIG. 3a, as controlled by a signal CAC of decoder 23 of FIG. 2, through time T_(m) of FIG. 3a. At time T_(m) associated with pulse MS of FIG. 5, a signal FFO at an output terminal 27a of a flip-flop 27, toggles from a first logical level to a second logical level, as illustrated in FIG. 3c. Flip-flop 27 signal FFO of FIG. 5 toggles after receiving, at a clock input terminal 22b, the leading edge of control pulse MS. After time T_(m), and until interval T end time T_(e) of FIG. 3a, as controlled by signal CAC, individual sync words SY are additively accumulated in accumulator 26 to provide an output word ACW that contains the total accumulation of the substractions and the subsequent additions.

In a second timing example of FIG. 3a, sync words SY, referred to as sync words SY2, are illustrated schematically by vertical arrows that define an envelope 2. Envelope 2, that is illustrated by the dotted lines, has a leading edge 70 and a trailing edge 71, that are similar to the respective edges in envelope 1. Words SY2 are provided within an interval T₂ that is equal in length to interval T. A center point T_(c2) of interval T₂ is delayed relative to center point T_(c) of interval T. Note that each word SY2 is of a smaller value at leading edge 70 but of a larger value at trailing edge 71 of envelope 2 than the corresponding words SY1 of leading edge 72 and trailing edge 73, respectively, of envelope 1. Therefore, the sum total in word ACW, at an end time T_(e2) of period T₂, is more positive than at end of time T_(e) of period T. Thus, the magnitude of word ACW is proportional to the length of the corresponding interval T_(c2) -T_(m) or T_(c) -T_(m). It follows that the magnitude and polarity values of word ACW correspond with the time difference, (T_(c) -T_(m)), between actual center point T_(c) of interval T and time T_(m) that is defined by the leading edge of pulse MS of FIG. 3b.

Output word ACW of accumulator 26 of FIG. 5 is coupled to an input port 28a of a scaler 28. Scaler 28 generates from word ACW a word SCW that expresses the time difference, (T_(c) -T_(m)) of FIG. 3a as a ratio n that is equal, illustratively, to (T_(c) -T_(m))/t_(CK). Ratio n has a resolution of time difference (T_(c) -T_(m)), illustratively, of 1/32 of clock CK period t_(CK).

Word SK of FIG. 2, that contains fraction f, is coupled to a port 22d of subtractor 30 of FIG. 5 where it is subtracted from word SCW to form a word SCWD at an input port 22g of a register 31. Register 31 stores each word SCWD and transfers it to an output port 22e to provide a phase word PH of FIG. 5. Phase word PH, that is, consequently, equal to [(T_(c) -T_(m))/t_(CK) -f], is clocked into and out of register 31 by a pulse CC of decoder 23 of FIG. 2 that is coupled to a clock terminal 22c at instant T_(r) of FIG. 3e following end time T_(e) of period T of FIG. 3a.

A time T_(cc) =T_(m) +f×t_(CK), as described later on, represents the calculated, or expected, occurrence time of the center of period T of FIG. 3a. The interval between time T_(cc) and the corresponding time t_(CMao) of event e_(CMao) is inherently equal to a predetermined integer multiple of clock CK periods t_(CK) of FIG. 3d. It follows that time T_(cc) is also periodic with the same period length of (M+k)×t_(CK) as time t_(CMao) of event e_(CMao) of FIG. 4d. Thus, in order to synchronize the occurrences of events e_(CMao) to the corresponding sync pulses H_(s) of FIG. 4r, it is sufficient that the actual center point T_(c) of period T of FIG. 3a coincides with the calculated time T_(cc). Word PH of FIG. 2 that is equal to [(T_(c) -T_(m))/t_(CK) -f], is thus indicative of the time difference between the actual center point T_(c), and the calculated center point T_(cc) of interval T of FIG. 3a. When word PH of FIG. 2 is positive, the actual center time T_(c) of FIG. 3a is greater, or later, than the calculated center time T_(cc). Conversely, when word PH of FIG. 2 is negative, the actual center time T_(c) of FIG. 3a is smaller, or earlier, than the calculated center time T_(cc). When time T_(cc) is equal to time T_(c), phase word PH of FIG. 2 is zero.

Phase word PH is coupled through a conventionally built digital low pass filter 32 of FIG. 2 to an input port 33b of an adder 33 to form filter 32 output word LPFO. Filter 32 may comprise an accumulator that additively accumulates individual phase words PH, under the control of a horizontal rate pulse CLPF generated by decoder 23 at a corresponding time T_(s) of FIG. 3f. Time T_(s) appears after time T_(r) of pulse cc of FIG. 3e. When phase word PH of FIG. 2 is zero, in the steady state example, word LPFO of low pass filter 32 does not change. A negative phase word PH, for example, decreases the value of word LPFO; whereas a positive phase word PH increases it. The adder of generator 33 adds word PR that represents the nominal number of clock CK periods t_(CK) contained in a given period H of the NTSC composite television signal, to the integer part of word LPFO for forming deflection period word DPW at port 33a. As described before, period length word DPW is added with 1H skew word S to produce updated words PERIOD and SK when pulse CL occurs at time T_(t) of FIG. 3g. Time T_(t) occurs shortly after time T_(s) of FIG. 3f.

Assume, hypothetically, that actual center time T_(c) of FIG. 3a is later than calculated center time T_(cc) ; consequently, phase word PH of FIG. 2 is of a positive value. Word DPW becomes larger when phase word PH becomes more positive. In the subsequent interval T of FIG. 3a, the larger word DPW produces calculated center time T_(cc), representing a longer time interval from the previous time T_(cc). Thus calculated center time T_(cc) becomes closer to actual center time T_(c) for achieving synchronization. In a steady, or synchronized, state, clock CK edge of FIG. 3d at time T_(m), occurs a fraction of clock CK period t_(CK), that is equal to f, prior to actual center point T_(c) of interval T of FIG. 3a. In the steady, or synchronized, state, each of events e_(CMao) and e_(CMbo) of FIGS. 4d and 4i, respectively, that are associated with words CMa and CMb, respectively, of FIG. 2, occurs a corresponding constant delay time, respectively, from the corresponding horizontal sync pulses H_(s) of FIG. 4r.

When output signal TOGGLE, of flip-flop unit 55 at select terminal 40c of multiplexer 40 of FIG. 2, is at the first logical state, words CMa in port 40a are coupled right adjusted to port 51a of programmable delay 51 that comprises an adder. Phase shifting word LPFO' of phase-control-loop circuit 120 is coupled, right adjusted, to port 51b of the adder of programmable delay 51. Word CMI at output port 51c of adder, or delay, 51, representing the integer part of the result of the addition in programmable delay 51, as illustrated schematically in FIG. 4k, is coupled to a zero detector 52. Zero detector 52 generates a pulse START at time T_(CMIO) of FIG. 4m, when word CMI of FIG. 4k becomes zero. Pulse START of FIG. 2 is coupled to pulse generator unit 53 causing it to generate, in a conventional manner, pulse PGP having a width w that is controlled by external controlling word WIDTH. Word WIDTH is coupled to an input port 53c of pulse generator 53. Pulse PGP is coupled to gate delay 54 that delays each individual pulse PGP by a fraction q of clock CK period t_(CK), thus producing a corresponding individual pulse h_(d) component of signal HORDRIVE of FIG. 4n. Fraction q of word CMP at output port 51c of adder 51 of FIG. 2 represents the fractional part of the result of the summation at the adder of programmable delay 51. The width w of pulse h_(d1) of FIG. 4h is, illustratively, wide enough to overlap the corresponding width of pulse f_(b1) of FIG. 4q.

Gate delay 54 may include a delay line of t_(CK) time delay, having, for example, 32 uniformly distributed taps. A given 5-bit combination of word CMP of FIG. 2 may select a corresponding tap of the 32 taps for delaying pulse PGP a fraction of clock CK period t_(CK) in accordance with its numerical value. For example, when fraction q of word CMP is equal to (00101)₂, the delay obtained is equal to (5/32)×t_(CK). Thus, an individual component pulse h_(d1) of signal HORDRIVDE of FIG. 4n occurs, for example, at time (T_(CMIO) +q₁ ×t_(CK)), where q₁ is the fraction contained in word CMP of FIG. 2.

After, for example, the occurrence of the trailing edge of pulse h_(d1) component of signal HORDRIVE of FIG. 4n, signal TOGGLE changes its state to be at a second state, as illustrated in FIG. 4p. Now signal TOGGLE causes words CMb in port 40b of multiplexer 40 of FIG. 2 to be coupled to port 51a of programmable delay 51 in the form of words CMI and CMP at its output port 51c. Zero detector 52 now generates pulse START at time T_(CMIO) ' of FIG. 4m, when word CMI of FIG. 4k at port 51c of programmable delay 51 of FIG. 2, becomes zero. This is done in a similar manner that was described before with respect to time T_(CMIO). Time T_(CMIO) ' of FIG. 4m is thus determined now by words Cb of FIG. 4h. The ensuing trailing edge of pulse h_(d2) component of signal HORDRIVE of FIG. 4n will cause flip-flop unit 55 of FIG. 2 to revert back to the first state, as illustrated in FIG. 4p, for coupling, as explained before, words Ca and SK of each word CMa at port 40a to port 51a of programmable delay 51 of FIG. 2. Thus, in accordance with an aspect of the invention, the timings of alternate first and second component pulses h_(d) of signal HORDRIVE of FIG. 4n that generates corresponding cycles of the deflection current that forms line deflection cycles at the 2f_(H) rate and that may be provided on the same signal line, such as, for example, at terminal 41a, of FIG. 2, are controlled, alternately, by words CMa and CMb in ports 40a and 40b, respectively, of multiplexer 40.

Each pulse FLYBACK of output stage 41 having illustratively, a trapezoidal shape, as illustrated in FIG. 4q, and derived from horizontal flyback pulses, may be digitized in a digitizer unit 61', that is analogous to digitizer unit 61, to form successive digitized flyback words SY' at an input port 22a' of a phase comparator 22'. Flyback words SY' of phase-control-loop circuit 120 are analogous to sync words SY of phase-lock-loop circuit 20. Phase comparator 22' may be constructed similarly to phase comparator 22 of phase-lock-loop circuit 20. Thus, ports 22a'-22e' of phase comparator 22' respectively, are functionally equivalent to ports 22a-22e, respectively, of phase comparator 22. A decoder 23' decodes corresponding predetermined values of words Ca for generating pulses MS' CAC', CC' and CLPF', respectively, that are analogous to pulses MS, CAC, CC and CLPF, respectively, of decoder 23. Pulse CC', for example, is coupled to terminal 22c'. Skew word SK is similarly coupled to port 22d' of phase comparator 22'.

Assume that flyback words SY', representing a trapezoidal envelope that is similar to envelope 1 of sync words SY of FIG. 3a, for example, are consecutively generated during a retrace interval T' of FIG. 4q that has an actual center time T_(c) '. Interval T' and center time T_(c) ' are analogous to interval T and center point T_(c) of FIG. 3a, respectively. In the example of FIG. 4q, the leading edge of pulse MS' of FIG. 2, that is coupled to terminal 22b' of phase comparator 22', occurs at time t_(CTJ) of FIGS. 4d as illustrated in FIG. 4o. In an analogous manner to the operation of phase comparator 22, a phase word PH' at port 22e' of phase comparator 22' of FIG. 2 is indicative of the corresponding time difference (T_(c) '-t_(CMao)). The term t_(CMao) in phase word PH', is analogous to the term T_(cc) in phase word PH of phase comparator 22. Using the same analogy, it follows that when center point T_(c) ' of interval T' of an individual pulse f_(b1) of pulses FLYBACK of FIG. 4q is greater than the corresponding time t_(CMao) of FIG. 4d, phase word PH' of FIG. 2 is positive. On the other hand, when time T_(c) ' of FIG. 4q is equal to time t_(CMao), phase word PH' of FIG. 2 is zero.

Phase word PH' of FIG. 2 is coupled to a sign complementing unit 58 that provides a sign complemented word PHi. When word PH' is negative, for example, word PHi is positive and of, illustratively the same absolute value as word PH'. Words PHi are coupled to a low pass digital filter 32' that is analogous to filter 32 of phase-lock-loop circuit 20. Filter 32' output word LPFO' has a shorter response time to phase variations of pulses FLYBACK of FIG. 4q than the response time of low pass filter 32 to phase variations of pulses H_(s) of FIG. 4r. In the steady state of phase-control-loop circuit 120 of FIG. 2, occurring when phase word PH' is zero, word LPFO' is negative with such a value that causes center point T_(c) ', of alternate pulses f_(b1) and f_(b3) pulses FLYBACK of FIG. 4q, to occur at times t_(CMao) and, t_(CMao), respectively, of FIG. 4d. It can be shown that component pulse h_(d1), for example, of signal HORDRIVE of FIG. 4n, occurs prior to the corresponding time t_(CMao) of FIG. 4d by a period t_(LEAD) that is equal to (Q+h)×t_(CK), where Q and h are the integer and fractional parts respectively, of word LPFO' of FIG. 2.

Word NPW of FIG. 2, that is coupled to the adder of programmable delay 42, controls the relative timing between pulse MS' of decoder 23' and the corresponding pulse MS of decoder 23. By changing the value of word NPW a corresponding change of the duration between, for example, center times T_(c) ' and T_(c) of pulses f_(b1) and H_(sa) of FIGS. 4q and 4r, respectively, is obtained.

As a result of a beam current change in the picture tube, the ultor current changes. The ultor current change that is coupled to the flyback transformer of output stage 41 causes the delay between pulse f_(b1) of FIG. 4q and pulse h_(d1) of FIG. 4n also to change because of switching time change. Assume that as a result of such change in delay, the interval (T_(c) '-t_(CMao)) of pulse f_(b1) of FIG. 4q deviates from zero and becomes positive. In this case, word PH' of FIG. 1 becomes more positive and word LPFO' becomes more negative. Therefore, the next pulse h_(d3) of FIG. 4n occurs earlier, causing pulse f_(b3) of pulses FLYBACK of FIG. 4q to occur earlier. This leads to a decrease in the length of the subsequent interval (T_(c) '-t_(CMao) ') so as to correct for the assumed deviation caused by the corresponding beam current change.

The same value of word LPFO' of FIG. 2 controls the timings of successive pulses h_(d) of FIG. 4n that correspond with events e_(CMao) and e_(CMbo), respectively. Because, for example, time t_(CMbo) of FIG. 4i is spaced from time t_(CMao) of FIG. 4d by a period length of H/2, as shown in FIG. 4q and as described before, pulse f_(b2) of flyback pulses FLYBACK of FIG. 4q that corresponds with time t_(CMbo) of FIG. 4i, appears H/2 after the immediately preceding pulse f_(b1) of pulses FLYBACK of FIG. 4q. Pulse f_(b1) corresponds with time t_(CMao) of FIG. 4q. Thus updating low pass filter 32' by pulse CLPF' of FIG. 2 occurs once in each horizontal period H. It should be understood that decoder 23' may be designed so that updating low pass filter 32' occurs at a rate of, illustratively, 2f_(H) that corresponds with the rate of flyback pulses FLYBACK of FIG. 2q.

When sync pulses H_(s) of FIG. 2 are absent, causing word LPFO of filter 32 to be zero, word DPW, which is equal to word PR=910, causes the arrangement of FIG. 1 to form retrace intervals separated by 910/2×t_(CK), that is equal to 1/2 the nominal value of period H in an NTSC system. 

What is claimed:
 1. A television apparatus for generating from a periodic, scanning frequency, synchronizing input signal, an output signal that is periodic at a frequency greater than said scanning frequency, comprising:a source of said synchronizing input signal; means responsive to said input signal for developing a part length signal that is indicative of the length of a part period of said synchronizing input signal; means responsive to said synchronizing input signal for generating a first periodic signal; means responsive to said part length signal for time shifting said first periodic signal by an amount that is determined in accordance with said length to generate a second periodic signal; and means responsive to said first and second periodic signals for generating said output signal therefrom.
 2. An apparatus as recited in claim 1 wherein each of said first and second periodic signals is periodic at said scanning frequency and wherein said output signal generating means includes means for combining said first and second periodic signals to generate said output signal that is periodic at the greater frequency.
 3. An apparatus as recited in claim 2 wherein said combining means comprises a multiplexer.
 4. An apparatus as recited in claim 1 wherein said first periodic signal generating means comprises a source of a clock signal, a counter responsive to said clock signal for generating said first periodic signal, means responsive to said synchronizing input signal for generating a scanning period length signal representative of the number of cycles of said clock signal indicative of the length of a scanning period and means responsive to said scanning period length signal for controlling counter operation in accordance with said synchronizing input signal, and wherein said part length signal developing means computes the number of cycles of said clock signal that is indicative of the length of said part period.
 5. An apparatus as recited in claim 4 wherein said part length signal developing means comprises a divider.
 6. An apparatus as recited in claim 4 wherein said time shifting means comprises an adder coupled to said counter and to said part length signal developing means.
 7. An apparatus as recited in claim 4 wherein said period length signal generating means comprises a phase detector responsive to said synchronizing input signal and to an output of said counter for generating a phase detector output signal representative of the deviation between said synchronizing input signal and said first periodic signal and wherein said part length signal developing means is responsive to an output of said phase detector.
 8. An apparatus as recited in claim 4 wherein said first periodic signal is generated from an output of said counter.
 9. An apparatus as recited in claim 4 further comprising a skew generator that is responsive to said input signal for generating a skew signal that provides a numerical value representative of a fraction of the period of said clock signal, wherein said skew signal is coupled to said time shifting means for generating said second periodic signal therefrom.
 10. An apparatus as recited in claim 4 wherein said part length signal developing means computes an integer number of cycles and a fraction of cycle of said clock signal that are indicative of the length of said part period to develop integer and fraction representative signals, respectively, of said part length signal.
 11. An apparatus as recited in claim 4 wherein said time shifting means generates integer and fraction part signals of said second periodic signal that supply timing information thereof wherein said integer part signal is indicative of a corresponding cycle of said clock signal and said fraction part signal is indicative of a corresponding cycle fraction of said clock signal.
 12. An apparatus for generating from a periodic synchronizing input signal, a time shifted first periodic output signal, comprising:a source of a clock signal; sequential means responsive to said clock signal for producing recurring sequences, each of which is associated with a corresponding cycle of said synchronizing input signal and each of which includes a plurality of sequential states that change from one state to the next at a time that is determined in accordance with said clock signal, said sequential means producing a second periodic signal that contains at a given time a value of a corresponding state in a given sequence; means responsive to said periodic input signal for generating a time shifting signal that contains a value that is substantially representative of an expected length of a predetermined portion of the period of said input signal; and means responsive to said time shifting signal for time shifting said second periodic signal to produce said first periodic output signal that is time shifted relative thereto by an amount that is substantially determined in accordance with said expected length.
 13. An apparatus as recited in claim 12 wherein said time shifting signal generating means includes means responsive to said input signal for generating a second signal that contains the value of the expected length of the period of said input signal for controlling the number of states in said given sequence, and means responsive to said second signal for dividing the value that is contained in said second signal by a predetermined factor for generating said time shifting signal.
 14. An apparatus as recited in claim 12 further comprising a phase-lock-loop circuit that is responsive to said input signal for generating a first skew signal that provides a numerical value representative of a fraction of the period of said clock signal, wherein said first skew signal is coupled to said time shifting means for time shifting said first skew signal.
 15. An apparatus as recited in claim wherein said first periodic output and second periodic signals are separated by an interval that is determined in accordance with said time shifting signal.
 16. An apparatus as recited in claim 15 further comprising means for combining said first periodic output and second periodic signals to form a third periodic output signal that is synchronized to and has a frequency greater than, said input signal.
 17. An apparatus as recited in claim 16 wherein the frequency of said third periodic output signal is an integer multiple of that of said input signal.
 18. An apparatus as recited in claim 16 wherein said combining means comprises a multiplexer that alternately couples said first periodic output and second periodic signals to form said third output signal.
 19. An apparatus as recited in claim 16 wherein said combining means forms integer and fraction part signals of said third periodic output signal that contain timing information thereof, wherein said integer part signal is indicative of a corresponding cycle of said clock signal and wherein said fraction part signal is indicative of a corresponding fraction of a cycle of said clock signal.
 20. A television apparatus responsive to a periodic, scanning frequency, synchronizing input signal for generating, a periodic output signal that is time shifted for generating, a periodic output signal that is time shifted relative to said input signal, comprising:a source of a periodic clock signal; a phase-lock-loop responsive to said input signal and to said clock signal for generating a first skew signal, providing a value representative of a fraction of the period of said clock signal such that both said clock and skew signals define a first periodic signal that is synchronized to said input signal; means responsive to said input signal for generating a time shifting signal that is indicative of the length of a part period of said input signal; time shifting means responsive to said time shifting signal for time shifting said skew signal by an amount that is determined by said time shifting signal to generate a second skew signal, providing a value representative of a corresponding fraction of the period of said clock signal, such that both said second skew and clock signals define said periodic output signal that is synchronized to said input signal and that is time shifted relative to said first periodic signal.
 21. An apparatus according to claim 20 further comprising means for combining said first and output periodic signals and for generating a second periodic signal at a frequency that is higher than that of each one of said first and output periodic signals.
 22. An apparatus according to claim 21 wherein said second periodic signal includes a skew signal that is determined in alternate periods of said second periodic signal in accordance with said first and second skew signals, respectively.
 23. A television apparatus responsive to a periodic, scanning frequency, synchronizing input signal for generating a periodic output signal comprising:a source of a periodic clock signal; means responsive to said input signal and to said clock signal for generating a periodic first skew signal, providing a value representative of a fraction of the period of said clock signal such that both said clock and skew signals form a first periodic signal that is synchronized to said input signal; time shifting means responsive to said first periodic signal for time-shifting thereof to generate a second skew signal, providing a value representative of a fraction of the period of said clock signal, such that both said clock and second skew signals form a second periodic signal that is synchronized to said input signal and that is time shifted relative to said first periodic signal; and means for combining said first and second periodic signals to form said output signal such that alternate periods of said output signal are determined in accordance with said first and second periodic signals, respectively.
 24. An apparatus according to claim 23 wherein the frequency of each of said first and second periodic signals is equal to that of said input signal and wherein said combining means generates said output signal at a frequency that is higher than that of said input signal.
 25. An apparatus according to claim 23 further comprising a deflection circuit output stage responsive to said output signal for generating deflection cycles at a frequency that is higher than that of said input signal. 